GPIB system with improved parallel poll response detection

ABSTRACT

A GPIB system including a parallel poll detection system for capturing signals of a GPIB in response to a parallel poll command. Capture logic includes sampling circuitry for continually sampling the GPIB signals, where the capture logic further stores the samples into a buffer upon desired conditions. A parallel poll detection circuit detects a parallel poll command asserted and subsequently negated on the GPIB, and correspondingly causes GPIB samples to be captured on both of these events. Also, a timer circuit causes the GPIB signals to be captured a predeteremined time period after the assertion of each parallel poll command. In the preferred embodiment, transition detect logic further causes GPIB samples to be captured if any transition of GPIB data signals occur while the parallel poll command is asserted on the GPIB.

CROSS-REFERENCE TO RELATED APPLICATIONS

This patent application relates to U.S. patent application Ser. No.08/473,110, filed on Jun. 7, 1995, entitled "GPIB System for CapturingGPIB Signals at a Predetermined Rate and Upon Transitions of the DataValid Signal"; U.S. patent application Ser. No. 08/473,200, filed onJun. 7, 1995 entitled "GPIB System Including Real Time Time-stamp"; U.S.patent application Ser. No. 08/472,967, filed on Jun. 7, 1995, entitled"GPIB System Including Deglitch Method and Apparatus to Assure ValidData Sampling"; and U.S. patent application Ser. No. 08/475,067, filedon Jun. 7, 1995, entitled "GPIB System Including Controller andAnalyzer". All of the applications are assigned to the same assignee.

FIELD OF THE INVENTION

The present invention relates to GPIB instruments, and more particularlyto a GPIB system with improved parallel poll response.

DESCRIPTION OF THE RELATED ART

Scientists and engineers often use laboratory and industrialinstrumentation systems to perform a variety of functions, includinglaboratory research, process monitoring and control, data logging,analytical chemistry, tests and analysis of physical phenomena andcontrol of mechanical or electrical machinery, to name a few examples. Aplurality of I/O interface options are available for allowingcommunication among various instrumentation systems, including the GPIB(general purpose interface bus), the VXI bus, the RS-232 interfaceprotocol, as well as data acquisition (DAQ) systems, as known to thoseskilled in the art. The present invention generally relates to the GPIBand related instruments.

The GPIB, otherwise referred to as the Institute of Electrical andElectronic Engineers IEEE-488 interface bus, was designed for remotecontrol of programmable instruments. Thousands of measurementinstruments from hundreds of suppliers are available with a GPIBinterface. GPIB instruments are typically more sophisticated and havehigher performance than other interface options, including DAQ andRS-232 boards. A plurality of instruments, usually up to 14, are coupledthrough a GPIB using eight-bit parallel protocol to achieve datatransfer rates of over one megabyte per second (MB/s). The GPIB devicescan be listeners, talkers and/or controllers. A talker sends datamessages to one or more listeners, which receive the data. Thecontroller manages the flow of information on the GPIB by sendingcommands to all devices. Some devices may perform several functions,such as a digital voltmeter which acts as a talker by sending voltageinformation on the GPIB and as a listener when receiving configurationand control information. Usually, there is only one controller for agiven GPIB where multiple GPIB devices are further coupled to the GPIBfor receiving command information from the controller for interfacingthe other GPIB devices. It is noted that some GPIB configurations do notrequire a controller if only one device would be considered a talker andthe remaining devices are listen-only devices. A controller is necessarywhen the active or addressed talker or listener must be changed orreconfigured where such control functions are usually handled by acomputer device. Also, there may be multiple controllers on a givenGPIB, although only one controller is the controller-in-charge (CIC) atany given time.

A high speed GPIB handshake protocol referred to as the HS488 isprovided to increase the data transfer rate of a GPIB system. The HS488protocol modifies the IEEE-488 source and acceptor handshake functionsto achieve the high speed data transfer rates of up to eight MB/s. Anydevices involved in HS488 compliant transfers must be compatible withthe HS488 protocol. However, non-HS488 devices may also be coupled to astandard GPIB, where the HS488 devices must use the standard handshakeprotocol to assure compatibility. According to the HS488 protocol, thedata valid (DAV) signal is asserted and held for a significant period,but the data signals themselves and an end or identify (EOI) controlsignal may only be valid for a short period of time, such asapproximately 20 ns, relative to the data valid (DAV) signal. A GPIBanalyzer is used to monitor a GPIB for testing and debugging purposes,where the analyzer captures data from the GPIB for display and analysis.One such example is the GPIB-410 by National Instruments Corporation(National Instruments), which is used in a similar manner as a logicanalyzer to monitor the control and data signals of the GPIB. Prior artGPIB analyzers usually sample data from the GPIB at a fixed rate.Although activity may not occur on a GPIB for a long period of time,when certain events do occur, such as data transfers according to HS488protocol, these events occur very quickly and should be sampled andcaptured appropriately. Sampling at a fixed rate, even if at a very fastrate of 50 nanoseconds (ns), may still miss important events such asdata signal changes which could potentially occur between 50 ns samples.This is particularly true on a GPIB also including HS488 compliantdevices, where data transfers occur very quickly when compared tostandard GPIB data transfer protocols. For example, 50 ns samples woulddetect changes of the DAV signal, but could potentially miss changes ofthe data and EOI signals since these signals remain valid for only avery short time period.

Most prior art GPIB analyzers connect to a GPIB system as a separateGPIB device. Thus, if a GPIB system contains the normal limit of 14devices, a device would have to be removed to add a prior art GPIBanalyzer to the GPIB system. Also, prior art GPIB analyzers are eitherstand-alone products containing a power supply and viewing screen, or anexpansion or circuit card designed to plug into a standard computer I/Obus, such as the industry standard architecture (ISA) bus. The prior artGPIB analyzer circuit card type further requires an additional I/O slotto any GPIB controller card which may be installed in the same computer.

It is further noted that it is often desired to determine the actual or"real" time that particular information or data was captured from theGPIB. Logic analyzers, for example, often attach a time-stamp value to aparticular piece of data captured from a group of signals or a bus. Thelogic analyzer includes a simple counter that may rollover or time-outseveral times, so that the time-stamp value does not indicate real timebetween capture events if one or more of such rollovers occur. Areal-time time-stamp requires a significantly large number of countersto indicate elapsed time with a desired degree of accuracy and timeincrement resolution. Otherwise, the counter circuitry rolls over andthe user may not be aware of such rollover. This leads to inaccurate orotherwise misleading results.

Prior art GPIB controllers and/or analyzers may obtain the status ofmultiple devices using the parallel poll command. Up to eight differentdevices can be configured to respond to the parallel poll command byassigning one of the eight GPIB data lines to each device. When thecommand is issued, each device asserts its assigned data line toindicate that the device is present on the GPIB and requesting service.The GPIB data byte is then retrieved for determining the status of theconfigured devices, where each data signal represents a one bit status.Prior art GPIB analyzers often yield inaccurate results because of theway the data is sampled during parallel polling. The response of thedevices may be delayed and there is no defined hold time for a device tohold its response valid. Some prior art analyzers retrieve data at afixed rate, so that the data could be retrieved before all of thedevices have had a chance to respond or after one or more of the deviceshave responded and have already negated their responses by the time thedata is sampled, thereby resulting in invalid or missed responses. Somedevices update their poll status bit during the parallel poll command,thus such updates may be missed by a fixed rate sampling device.

Some analyzers retrieve data both at the beginning and end of theparallel poll command. However, valid responses occurring during thecommand may still be missed. Still other analyzers sample only at theend of the parallel poll command, thus valid responses or updatedresponses may be completely missed. It is desired to handle all of thesecases and retrieve valid and updated responses.

In sum, it is desired to provide a GPIB analyzer with improvedperformance for capturing all important events occurring on a GPIB aswell as for time-stamping the captured events in real-time. It is alsodesired to provide a GPIB analyzer that does not require additionalcomputer or GPIB resources to those required by an existing GPIBcontroller.

SUMMARY OF THE INVENTION

A GPIB system according to the present invention includes a GPIBcontroller and a GPIB analyzer on the same circuit card. The combinedcontroller and analyzer functions require a single connection to theGPIB and a single I/O slot in a host computer.

The GPIB system includes sampling logic for sampling the GPIBsynchronously or at a predetermined rate, as well as for sampling theGPIB asynchronously, or according to changes of the DAV signal. Thistechnique allows data to be captured at a regular interval as well as onedge transitions of the DAV signal. The synchronous logic samples dataonce every 50 ns. For edge transition capturing, the DAV signal itselfis used as the sampling event to clock a set of flip-flops to assurethat valid data is not missed by the synchronous logic. Data valid logicdetects valid transitions of the DAV signal and provides a datatransition select signal to select logic, which switches between thesynchronous GPIB samples and the asynchronous GPIB samples. The selectedsamples are provided to and stored in a buffer, such as a first in,first out (FIFO) buffer. Capture logic monitors the sampled GPIB signalsand the data transition select signal and enables the buffer to capturethe selected sample upon predetermined capture conditions. In thismanner, the correct data is detected and captured into the buffer evenduring fast data transitions.

Sampling data from the GPIB based on the DAV signal could result inerroneous data since the DAV signal tends to exhibit false transitions.A unique data valid deglitch circuit detects such glitches of the DAVsignal and thereby separates valid from invalid DAV transitions. Thisassures that valid data is captured into the buffer. The deglitchcircuit is preferably programmable for filtering false transitions ofthe DAV signal based on a clock signal. The deglitch circuit preferablyincludes a first memory circuit for detecting the DAV signal remainingasserted for at least two consecutive transitions of a clock signal anda second memory circuit for detecting the DAV signal remaining assertedfor three consecutive clock transitions. A programmable memory circuitselects between the first and second memory circuits. Also, the deglitchcircuit can include further memory circuitry for detecting the DAVsignal asserted for five consecutive transitions of the clock circuit.The user can program the memory circuit to select between any one ofthese three conditions. Each of the memory circuits preferably comprisesa set of flip-flops.

A time-stamp timer may be enabled to provide a real-time time-stampvalue for each set of data captured into the buffer. If enabled, thecapture logic asserts a time-stamp select signal to the select logic andenables the buffer for inserting the time-stamp value into the bufferafter each capture. In this manner, all of the important transitionsoccurring on the GPIB are captured into the FIFO along with a real-timetime-stamp value identifying when each capture occurred.

The timer includes a counter which provides a relative elapsed timebetween captures, where the capture logic resets the counter after eachcapture. In the preferred embodiment, the timer is a 16-bit counterincremented every 50 ns, which does not rollover until afterapproximately 3.28 milliseconds (ms). Upon such rollover, the counterasserts a time-out signal to the capture logic, which correspondinglyenables the maximum timer value of FFFFh (a lower-case "h" indicatinghexadecimal) to be written into the buffer. The FIFO is preferably a 2Kby 18 bit buffer including two extra bits for each 16-bit data value.One of the extra bits is preferably set for the first rollover ortime-out value, thereby marking the first time the timer times out. Aninterrupt is generated when this buffer location is read to alert thesoftware to count remaining time-out values in order to compute thetotal elapsed time between true data values captured from the GPIB. Thesoftware easily calculates the real time between each of the truecapture data values by summing any time-out values multiplied by 3.28ms, as well as by multiplying other time-stamp values by 50 ns.

In this manner, a real-time timer marks all significant events on theGPIB with a relatively high resolution, which is preferably achievedusing a single 16-bit counter clocked every 50 ns. It is noted thatsince time-out occurs only once every 3.28 ms during long periods ofinactivity, the software is easily able to keep up with the FIFO,thereby preventing overflow of the FIFO. In an alternative embodiment,each time-stamp value captured into the FIFO is compared with themaximum value (FFFFh) so that the marking and interrupt method need notbe used. This embodiment is preferred for certain applications whichhave a significant amount of overhead associated with interrupts. Ineither embodiment, elapsed time between capture events is easilycalculated and provided to the user.

A GPIB system according to the present invention retrieves all valid andupdated responses to a parallel poll command. The GPIB data is capturedimmediately after a parallel poll command is issued as well as after thecommand is deasserted. Also, a timing device causes another sample to becaptured after approximately 2 microseconds (μs) to give the devicestime to provide a valid response. Furthermore, more samples are capturedduring any data line transitions that occur while the parallel pollcommand remains asserted. This assures that any initial and updatedresponses are captured during the command, which would otherwise bemissed in prior art embodiments.

Therefore, a GPIB system according to the present invention capturesimportant events occurring on the GPIB into a buffer in an accuratemanner. Also, a timer provides a real-time time-stamp value, which isinserted into the buffer following each associated captured value ifdesired. The real-time time-stamp has a high resolution and provides anaccurate temporal determination of each captured value. Furthermore,both controller and analyzer functions are included for conservingcomputer resources.

BRIEF DESCRIPTION OF THE DRAWING

A better understanding of the present invention can be obtained when thefollowing detailed description of the preferred embodiment is consideredin conjunction with the following drawings, in which:

FIG. 1 is a simplified block diagram illustrating a GPIB systemincluding a GPIB analyzer according to the present invention;

FIG. 2 is a diagram illustrating the standard GPIB signals;

FIG. 3 is a simplified block diagram of a GPIB system according to thepresent invention including analyzer and controller functions;

FIG. 4 is a simplified block diagram of the GPIB analyzer portion of theGPIB system of FIG. 3;

FIG. 5 is a schematic diagram illustrating the logic for capturing GPIBcontrol signals;

FIG. 6A is a schematic diagram illustrating logic for capturing the datasignals of the GPIB;

FIG. 6B is a schematic diagram illustrating logic for capturing the endor identify control signal of the GPIB;

FIG. 7A is a schematic diagram of the logic for identifying theassertion of the DAV signal of the GPIB;

FIG. 7B is a schematic diagram of the deglitch circuit of FIG. 7A;

FIGS. 7C and 7D are timing diagrams illustrating operation of thedeglitch circuit of FIGS. 7A and 7B;

FIG. 8 is a schematic diagram of the time-stamp timer of FIG. 4;

FIG. 9 is a schematic diagram illustrating logic for performing parallelpoll;

FIGS. 10A and 10B are simplified logic diagrams illustrating logic foridentifying predetermined capture conditions of the control and datasignals, respectively;

FIG. 11 is a schematic diagram of the logic for identifying all captureconditions on the GPIB;

FIGS. 12A and 12B illustrate a capture logic state machine and itsoperation; and

FIG. 13 is a schematic diagram of the multiplexer logic for capturingdata into a FIFO buffer.

DETAILED DESCRIPTION OF THE PREFERRED EMBODIMENT

Referring now to FIG. 1, a simplified block diagram is shown of a GPIBsystem 100 including a GPIB analyzer and controller card 106 implementedaccording to the present invention. A computer 102, which is preferablya personal computer (PC) such as the XT or AT by IBM, includes aninput/output (I/O) or expansion bus 104 which is preferably based on theindustry standard architecture (ISA) also referred to as the AT bus. Itis noted that the computer 102 may be any one of several known typessuch as the Apple Computer or Macintosh or may include any one ofseveral work stations such as the Sun SPARCstation, etc. The expansionbus 104 could alternatively be based on the Extended ISA (EISA), thePCMCIA standard or the PCI (peripheral component interconnect) bus orany one of the known I/O or expansion buses of computer systems.

A GPIB analyzer/controller card 106 plugs into one of the I/O slots ofthe computer 102 for connecting to the expansion bus 104 of the computer102. The GPIB analyzer/controller card 106 couples the computer 102 to aGPIB 108, also known as the IEEE 488 interface bus. At least one andnormally a plurality of GPIB devices 110 are further connected to theGPIB 108 in any one of several known methods, such as series or starconfigurations, etc. Each of the GPIB devices 110 may be any one ofthousands of instruments adapted for communicating on the GPIB 108. Inthis manner, the computer 102, through the GPIB analyzer/controller card106, controls all of the GPIB devices 110 on the GPIB 108. Each of theGPIB devices 110 can be listeners, talkers and/or controllers as knownto those skilled in the art. In the preferred embodiment, the GPIBanalyzer/controller card 106 includes the primary controller of the GPIB108 for controlling each of the GPIB devices 110. As will be describedmore fully below, the GPIB analyzer/controller card 106 further includesthe GPIB analyzer for monitoring signals on the GPIB 108 for testing anddebugging purposes by capturing data or control signals from the GPIB108 for display and analysis.

The computer 102 may include bridge logic 120 for coupling the expansionbus 104 to a system (or local) bus 122, although other configurationsare contemplated. The computer 102 further includes a microprocessor124, such as an 80386, i486 or Pentium processor by Intel, and mainmemory 126 coupled to the system bus 122. Of course, the computer 102also typically includes a monitor 130 and associated graphics controller(not shown) as well as input devices such as a keyboard 132 and mouse134. In this manner, the user loads software routines into main memory126 (from data drives, etc.) for execution by the microprocessor 124 forsending and receiving data and commands for programming and controllingthe GPIB analyzer/controller card 106, and for ultimately controlling orotherwise monitoring the GPIB 108 and associated GPIB devices 110.

Referring now to FIG. 2, a diagram is shown of a GPIB connector withstandard signal assignment as known to those skilled in the art. Pinnumbers 1-4 and 13-16 comprise the eight-bit data bus of the GPIB 108,including data bus signals DIO1-DIO8, otherwise referred to as the DIOsignals. The connector 200 includes three handshake signals forasynchronously controlling the transfer of message bytes between theGPIB devices 110 for guaranteeing that data is sent and received withouttransmission error. The handshake lines include a not ready for data(NRFD) signal which indicates when a device is ready or not ready toreceive a message byte. The NRFD signal is driven by any devicereceiving commands, by listeners when receiving data messages, and by atalker when enabling the HS488 mode. A not data accepted (NDAC) signalindicates when a device has or has not accepted a message byte. The NDACsignal is driven by any of the GPIB devices 110 when receiving commandsand by listeners when receiving data messages. A data valid (DAV) signalindicates when the DIO signals are stable and valid and thus can beaccepted safely by any of the GPIB devices 110. The GPIBanalyzer/controller card 106 drives the DAV signal when sendingcommands, and a talker drives the DAV signal when sending data messages.

The GPIB 108 further includes five interface management signals formanaging the flow of information across the GPIB 108. An attention (ATN)signal is driven by the GPIB analyzer/controller card 106 when using theDIO data signals to send commands, and otherwise drives the ATN signallow to allow a talker to send data messages. An interface clear (IFC)signal is driven by a controller to initialize the GPIB 108 and toestablish that controller as the controller-in-charge (CIC). A remoteenable (PEN) signal is driven by the controller to place the devices inremote or local program mode. A service request (SRQ) signal is drivenby any one of the GPIB devices 110 to asynchronously request servicefrom the GPIB analyzer/controller card 106. Finally, an end or identify(EOI) signal is used by a talker to mark the end of a message string andis alternatively used by the controller to tell the GPIB devices 110 toidentify their response in a parallel poll command.

Referring now to FIG. 3, a block diagram is shown of the GPIBanalyzer/controller card 106 implemented according to the presentinvention. The expansion bus 104 includes control (C), address (A), anddata (D) signals connected to the primary controller portion referred toas the TNT 308, which is preferably the TNT4882C ASIC by NationalInstruments but may be any GPIB controller circuit such as the NEC 7210.The TNT 308 is further connected to the data (D) and control (C) signalsof the GPIB 108. The TNT 308 preferably performs the basic IEEE 488talker, listener, and control functions required by the ANSI/IEEE 488.2standard (ANSI is the American National Standard Institute). In thepreferred embodiment using the ISA expansion bus, the TNT 308 preferablycan sustain data transfers up to 1.5 MB/s using the IEEE 488.1 standardthree-wire handshake. The TNT 308 also preferably implements the highspeed GPIB protocol (HS488) for data transfers up to 1.6 MB/s on an ISAplatform or 3.4 MB/s on a computer system incorporating the EISAplatform. It is noted that for embodiments using different expansionbuses, the TNT data transfer rates may vary. The TNT 308 is also used tomonitor the GPIB 108 as well as to provide device emulation, sourcehandshaking, and pattern generation.

Preferably, a bus interface chip 310 provides a chip select to the TNT308 and to the primary analyzer portion, referred to as the FPGA 304. Inthe preferred embodiment, a bus interface chip such as the NM95MS15Pfrom National Semiconductor that conforms to the ISA Plug and Playspecification is used. The bus interface chip 310 preferably interfacesDMA (direct memory access) channels and interrupt request signals (IRQ)to the expansion bus 104. The FPGA 304 controls the capturing of thestatus of the GPIB 108 into a high speed 2K by 18 bit FIFO 300. Throughthe FPGA 304, the GPIB analyzer/controller card 106 can be configured tocapture and/or trigger on any transition or state of interest on theGPIB 108. The captured status is then read from the FIFO 300 by thecomputer system 102 for analysis and display on the monitor 130, ifdesired. An oscillator 302 provides a 40 MHz clock signal (CLK) to theFIFO 300, the FPGA 304, and the TNT 308. The CLK signal is used todevelop two clock signals internal to the FPGA 304, one having a 25 nsperiod referred to as CLK25 and another having a 50 ns period referredto as CLK50. Also, GPIB drivers and receivers 306 provide interfacing ofthe FPGA 304 to the GPIB 108, where the GPIB drivers and receivers 306are used by the FPGA 304 to independently assert the control signals ofthe GPIB 108 for the acceptor handshake and to receive the signals ofthe GPIB 108 for capturing.

Referring now to FIG. 4, a block diagram is shown of the FPGA 304coupled to the expansion bus 104, to the GPIB 108, and to the FIFO 300.Bus interface logic 400 decodes register accesses to the otherfunctional blocks within the FPGA 304 and couples to the DMA logic 402and the interrupt logic 404 to generate DMA and interrupt requests. TheDMA logic 402 is connected to a FIFO interface 406 in order to detectwhen data is present in the FIFO 300 so that DMA may be requested tounload data from the FIFO 300. The FIFO interface 406 provides thecontrol signals to read data from or write data to the FIFO 300.

The primary function of the FPGA 304 is to capture the state of thecontrol and data signals of the GPIB 108 based on certain programmedconditions. The control and data signals of the GPIB 108 are all sampledevery 50 ns by capture logic 410. Also the DIO and EOI signals aresampled upon assertion edge transitions of the DAV signal. Thisasynchronous sample of the DIO and EOI signals is desired because theymight otherwise be missed at the 50 ns fixed rate if HS488 transfers areused. If a programmed capture condition is true, the sample retrieved bythe capture logic 410 is provided through the FIFO interface 406 to theFIFO 300. If the capture condition is not true, the sample retrievedfrom the GPIB 108 is discarded. A capture enable signal referred to asCAP₁₃ EN determines whether capturing is enabled or disabled. If theCAP₋₋ EN signal is true and the FIFO 300 is not full, capturing willtake place according to one of several capture conditions as follows:when a trigger condition is true; upon the occurrence of a parallel pollwhen a signal IDY is true, where IDY=ATN & EOI (FIG. 9); upon handshakeline transitions by monitoring state changes of the NDAC, NRFD and DAVsignals; upon control line transitions by monitoring the IFC, REN, ATNand SRQ signals for any state changes; upon command transfer when boththe ATN and DAV signals are true; upon data transfer when ATN is falseand DAV is true; upon data line transitions; upon time-stamp timerrollover of a time-stamp timer 408; and when a Force Capture PulseCommand is issued through software.

The time-stamp timer 408 includes a 16-bit counter circuit 800 (FIG. 8)preferably clocked by the CLK50 signal for a resolution of 50 ns perbit. Of course, other frequencies and resolutions are contemplated andare a matter of design choice. The timer 408 is used to determine theamount of time between capture events of the GPIB 108 through thecapture logic 410. Thus, whenever time-stamping is enabled, a time-stampvalue is written into the next location of the FIFO 300 after a sampleis captured into the FIFO 300 from the capture logic 410, as describedmore fully below. In this manner, the FIFO 300 contains GPIB samples andtime-stamp values in alternating locations.

Trigger logic 412 coupled to the GPIB 108, the bus interface logic 400and the capture logic 410 allows the FPGA 304 to trigger on anypredetermined pattern of signals appearing on the GPIB 108. The triggerpattern is specified and configured by a trigger and pattern register(TRPR) and a trigger mask register (TRMR). Setting a bit in the TRMRregister indicates that trigger logic 412 will treat the correspondingsignal on the GPIB 108 as a don't care. For each bit that is not setwithin the TRMR register, the trigger state of the signals of GPIB 108are determined by the state of the corresponding TRPR register bits.Thus, a trigger condition occurs when a sample of the GPIB 108 equalsthe pattern specified by the TRMR and TRPR registers. Thus, if capturingis enabled and if triggering bits are set, the current GPIB sample iscaptured into the FIFO 300 each time the trigger condition transitionsfrom false to true or alternatively, only the first time the triggercondition transitions from false to true.

Finally, the FPGA 304 is configured to participate in the GPIB handshakeas an acceptor through acceptor handshake logic 414. Participation inthe handshake is enabled by setting an HNSK₋₋ EN enable bit in ahandshake configuration register. Also, the acceptor handshake logic 414may be programmed to vary the rate of the GPIB acceptor handshake.

Referring now to FIG. 5, a schematic diagram is shown of the logic forsampling and comparing the control signals of the GPIB 108. Inparticular, all of the control signals except the EOI and DAV signals,including the IFC, REN, SRQ, ATN, NRFD and NDAC signals, arecollectively referred to as GPIB₋₋ CTL(0) as appearing at a time t=0relative to the CLK50 signal on the GPIB 108. The GPIB₋₋ CTL(t)designation represents individual signals IFC(t), REN(t), SRQ(t),ATN(t), etc. The EOI signal is handled in a similar manner as the DIOsignals, as described below. The DAV signal is handled in a differentway which is described below. The GPIB₋₋ CTL(0) signals are eachprovided to the D inputs of a set of six D-type flip-flops, collectivelyreferred to by the reference number 500. Only one flip-flop 500 isshown, it being understood that it is repeated six times for each of thecontrol signals of the GPIB 108. It is noted that any appropriate typeof latch or flip-flop may be used to sample signals of the GPIB 108,where D-type flip-flops are used in the illustrated embodiment. TheCLK50 signal is provided to the clock input of the flip-flops 500 forsampling the control signals of the GPIB 108 every 50 ns, where theinitial sampled versions are referred to as signals GPIB₋₋ CTL(1) at theoutputs of the flip-flops 500. This process is repeated again where theGPIB₋₋ CTL(1) signals are provided to the D inputs of another set of sixD-type flip-flops 502, which receive the CLK50 signal at their clockinputs. The flip-flops 502 provide signals GPIB₋₋ CTL(2) at their Qoutputs, representing latched versions of the GPIB₋₋ CTL(1) signalsafter 50 ns.

Each of the GPIB₋₋ CTL(2) signals are provided to one input of a set ofsix, two-input exclusive-OR (XOR) gates 504, where the GPIB₋₋ CTL(1)signals are provided to the other input of each of the XOR gates 504. Inthis manner, the XOR gates 504 provide a set of CAP₋₋ CTL_(n) signalsrepresenting change of state of the control signals of the GPIB 108between successive clock cycles of the CLK50 clock signal, for detectingcertain capture conditions as described below. The subscript "n"represents multiple signals, where CAP₋₋ CTL_(n) generally representsall of the signals CAP₋₋ IFC, CAP₋₋ REN, CAP₋₋ SQR, CAP₋₋ ATN, CAP₋₋ RFDand CAP₋₋ DAC denoting changes of the IFC, REN, SQR, ATN, NRFD and NDACsignals, respectively.

Referring now to FIG. 6A, a schematic diagram is shown for sampling anddetecting changes of the DIO signals on the GPIB 108. The DIO signals,collectively referred to as DIO(0), are provided to the D inputs of aset of eight D-type flip-flops 600, receiving the CLK50 signal at theirrespective clock inputs. The Q outputs of the flip-flops 600 providesignals DIO(1), which are latched versions of the DIO(0) signals. TheDIO(1) signals are provided to the D inputs of another set of eightD-type flip-flops 602, each receiving the CLK50 signal at theirrespective clock inputs. The Q outputs of the flip-flops 602 providelatched signals DIO(2) which are each provided to one input of a set ofeight two-input XOR gates 604. The DIO(1) signals are provided to theother respective inputs of the XOR gates 604, which provide a set ofeight CAP₋₋ DAT_(n) signals to the respective inputs of an eight inputOR gate 605, which asserts a signal CAP₋₋ DAT at its output. Thus, theCAP₋₋ DAT signal is asserted when any of the DIO signals change state.In this manner, the data signals of the GPIB 108 are sampled at 50 nsintervals in a similar manner as the control signals of the GPIB 108described above in FIG. 5, except that a single signal CAP₋₋ DATidentifies any changes of state of the DIO data signals.

The DIO(0) signals are also provided to the respective D inputs of a setof eight D-type flip-flops 606, each receiving the DAV signal at theirrespective clock inputs. In this manner, each of the DIO signalsappearing on the GPIB 108 are sampled with each assertion of the DAVsignal by the flip-flops 606, which provide signals DAV₋₋ DIO(1) attheir respective Q outputs. The DAV₋₋ DIO(1) signals are provided to therespective D inputs of a set of eight D-type flip-flops 608 receivingthe CLK50 clock signal at their respective clock inputs. The flip-flops608 provide a set of signals DAV₋₋ DIO(2) signals at their Q outputs. Inthis manner, the DIO(t) signals generally represent samples of the datasignals on the GPIB 108 at a fixed interval of 50 ns, whereas the DAV₋₋DIO(t) signals represent the data signals of the GPIB 108 when the DAVsignal is asserted. In this manner, very fast changes of the DIO datasignals, which might otherwise be missed by a fixed rate capture of 50ns are captured by the flip-flops 606.

Referring now to FIG. 6B, a schematic diagram is shown illustratinglogic for capturing the EOI signal of the GPIB 108, which is similar tothe logic for capturing the DIO data signals. The EOI signal is providedto the D inputs of two D-type flip-flops 610 and 616. The flip-flop 610receives the CLK50 signal at its clock input and provides a latchedEOI(1) signal at its Q output. The EOI(1) signal is provided to anotherD flip-flop 612, which is also clocked by the CLK50 signal for providinga signal EOI(2) at its Q output. The EOI(1) and EOI(2) signals areprovided to the respective two inputs of a two-input XOR gate 614, whichprovides a signal CAP₋₋ EOI at its output indicating changes of the EOIsignal. The flip-flop 616 is clocked by the DAV signal for sampling theEOI signal upon assertions of the DAV signal, where this sampled valueis provided as a signal DAV₋₋ EOI(1) at the Q output of the flip-flop616. The DAV₋₋ EOI(1) signal is provided to the D input of another Dflip-flop 618, which is clocked by the CLK50 signal for providing asignal DAV₋₋ EOI(2) at its Q output. In this manner, changes of the EOIsignal are sampled along with the DIO signals upon assertion transitionsof the DAV signal.

Referring now to FIG. 7A, a schematic diagram is shown illustrating thelogic for detecting transitions of the DAV signal on the GPIB 108. TheDAV signal is provided to a deglitch circuit 700, which provides asignal SDAV at its output. It is noted that spurious assertions of theDAV signal could cause erroneous collection of data which is not desiredby the user. Such erroneous data may be sampled by the flip-flops 606,but are not captured as described before. The deglitch circuit 700generally detects the spurious assertions of the DAV signal providing afiltered version as the SDAV signal. The SDAV signal is provided to theD input of a D-type flip-flop 704, receiving the CLK25 clock signal atits clock input, where the SDAV signal and the Q output of the flip-flop704 are both provided to the two inputs of an OR gate 706 for providingits output to the binary 0 input of a multiplexer (mux) 708. The DAVsignal is also provided to the binary 1 input of the mux 708, whichreceives an override signal OS at its select input. The output of themux 708 reflects the selected binary input based on the state of theselect signal provided to the mux 708.

A signal DG0 is provided to the non-inverted input of a two input ANDgate 718, which asserts the OS signal at its output. Another signal DG1is provided to the inverting input of the AND gate 718. As describedbelow, the DG0 and DG1 signals set timing parameters within the deglitchcircuit 700. The OS signal is asserted when deglitching is turned offand the deglitch circuit 700 is effectively bypassed. The output of themux 708 is provided to the D input of a D-type flip-flop 710, receivingthe CLK50 signal at its clock input. The Q output of the flip-flop 710,referred to as a signal SDAV1, is provided to the D input of a D-typeflip-flop 712 receiving the CLK50 signal at its clock input. The Qoutput of the flip-flop 712 is a signal SDAV2, which is provided to theinverting input of a two-input AND gate 714, which receives the SDAV1signal at its non-inverting input and which provides the CAP₋₋ DAV₋₋ASSRT signal at its output. The SDAV1 signal is provided to the invertedinput of another two-input AND gate 716, which receives the SDAV2 signalat its non-inverting input for providing the CAP₋₋ DAV₋₋ UNASRT signal.

Operation of the circuit shown in FIG. 7A is now described. It is notedthat the DAV signal valid transitions are normally held long enough forcapture by a 50 ns fixed rate sampling period. However, it is desirednot to capture sampled data in the event the DAV signal transition wasspurious and not associated with a valid data change. Any validassertions of the DAV signal on the GPIB 108 as detected by the deglitchcircuit 700 are asserted as the SDAV signal for at least 25 ns. The ORgate 706 detects any assertions or deassertions of the DAV signal. WhenOS is low, such assertions or deassertions are captured by the flip-flop710, which are provided to the flip-flop 712 and also to the AND gate714. Thus, the output of the AND gate 714 asserts the CAP₋₋ DAV₋₋ ASSRTsignal when the DAV signal is asserted from low to high during any 50 nsclock cycle. Deassertions or negations of the DAV signal are detected bythe AND gate 716 as the CAP₋₋ DAV₋₋ UNASRT signal in a similar manner.

Referring now to FIG. 7B, a schematic diagram is shown of the deglitchcircuit 700. The DAV signal is provided to the asynchronous clear inputsof four D-type flip-flops 720, 722, 726 and 730. The flip-flops 720,722, 726 and 730 receive the CLK25 signal at their clock inputs,although the flip-flops 722 and 726 invert the CLK25 signal and thus areclocked on the falling edges. The D inputs of flip-flops 720, 722 arefixed at a high logic level. The Q output of flip-flop 720 is providedto the D input of flip-flop 726, to the D input of another flip-flop 724and to the binary 1 input bit of a two-input mux 727. The flip-flop 724receives the CLK25 signal at its inverted clock input. The Q output offlip-flop 722 is provided to the binary 0 input of the mux 728, whichreceives the DG0 signal at its select input. The output of mux 728 isprovided to the D input of the flip-flop 730, which provides its outputto the D input of another flip-flop 732 receiving the CLK25 signal atits inverted clock input. The Q output of the flip-flop 732 is providedto one input of a two-input OR gate 734, which receives the Q output ofthe flip-flop 726. The output of the OR gate 734 is provided to thebinary 10 input of a three-input mux 738, which receives the DG1, DG0signals at its two select inputs and provides its output to the D inputof a D-type flip-flop 740. The flip-flop 740 receives the CLK25 signalat its clock input and provides the SDAV signal at its output. The Qoutputs of the flip-flops 722, 724 are provided to the respective inputsof a two-input OR gate 736, which provides its output to the binary 00input of the mux 738. The Q output of the flip-flop 730 is connected tothe binary 11 input of the mux 738.

The deglitch circuit 700 is programmed using the DG0 and DG1 signals toprovide pulse rejection and recognition according to the following table1:

                  TABLE 1                                                         ______________________________________                                        Programming values for the DAV Deglitch Circuit                               DG1, DG0                                                                              Max Pulse Rejected (ns)                                                                        Min Pulse Recognized (ns)                            ______________________________________                                        00        12.5           25                                                   01      not used - OS asserted                                                                         not used - OS asserted                               10      25                 37.5                                               11      50               75                                                   ______________________________________                                    

where the maximum pulse rejected indicates that the deglitch circuit 700will reject any pulse less than the indicated duration and the minimumpulse recognized indicates that the deglitch circuit 700 is guaranteedto recognize a pulse greater than the indicated duration. For clarity,the output signals of the flip-flops 720, 726, 724, 722, 730 and 732 areshown as signals A, B, C, D, E and F, respectively, although signals Eand F are referred to as two separate signals, E0, E1 and F0, F1,respectively, in timing diagrams (FIGS. 7C, 7D) depending upon the stateof the DG0 signal.

The general operation of the deglitch circuit 700 is now described. Themaximum rejected and minimum recognized pulse times are based ontransitions of the CLK25 signal. For the DG1, 0=00 case, a DAV pulsemust remain asserted during at least two consecutive transitions of theCLK25 signal, which means for more than 12.5 ns, to be detected by theflip-flop 740. Pulses less than to 12.5 ns do not meet this criterionand are rejected. It is noted that pulses exactly equal to 12.5, 25,37.5 ns etc. having edges concurrent with the CLK25 transitions may ormay not meet the timing parameters and are a matter of probability. Suchexact cases are considered trivial and will be ignored for purposes ofthis disclosure. For the DG1, 0=00 case, the A signal is asserted by theflip-flop 720 whenever the DAV signal is true on a rising edge of theCLK25 signal, but is only asserted while DAV is true. If DAV is true forat least 12.5 ns, then the flip-flop 724 asserts the C signal. Since theflip-flop 724 remains asserted for a full clock cycle, the flip-flop 740detects whether the DAV signal is asserted on a rising edge and lasts atleast until the following falling edge of the CLK25 signal. Theflip-flop 722 asserts the D signal when DAV is true on a falling edge ofthe CLK25 signal, but only for so long as DAV remains true. If DAVremains true for at least 12.5 ns until the following rising edge of theCLK25 signal, then the flip-flop 740 detects this pulse. In this manner,any pulse greater than 25 ns is guaranteed to be detected by theflip-flop 740, pulses less than 12.5 ns will always be rejected andthose between 12.5 and 25 ns that encompass two consecutive transitionsof CLK 25 are detected.

In a similar manner, a DAV pulse must remain asserted for threeconsecutive transitions of the CLK 25 signal (25 ns) to be detected whenDG1, 0=10. In this case, the B signal is asserted if the DAV pulse istrue on a rising edge and lasts at least until the following fallingedge. However, the flip-flop 740 only detects the assertion of the Bsignal if the DAV pulse remains asserted until the following risingedge, since otherwise the flip-flop 726 is cleared. Also, the F signalis asserted by the flip-flop 732 only if the DAV pulse is true on afalling edge as detected by the flip-flop 722, and if the pulse remainstrue until the next falling edge, since otherwise the flip-flops 722 and730 are cleared. Thus, the DAV pulse must be true for three consecutivetransitions of the CLK25 signal. Thus, pulses greater than 37.5 ns arealways detected while pulses less than 25 ns are always rejected. Pulsesbetween 25 and 37.5 ns are only detected as long as they encompass threeconsecutive CLK25 transitions.

For the DG1, 0=11 case, a DAV pulse must remain asserted for threeconsecutive rising edges of the CLK 25 signal (50 ns). The first andsecond rising edges are detected by the flip-flops 720 and 730,respectively, which are cleared unless the pulse remains asserted untilthe following rising edge of the CLK25, where the E signal is latched bythe flip-flop 740. Thus, pulses equal to or less than 50 ns are alwaysrejected while pulses greater than 75 ns are always detected. Again, anypulses having a duration between 50 and 75 ns are detected as long asthey remain asserted during three consecutive rising edges.

Referring now to FIG. 7C and 7D, timing diagrams are shown illustratingoperation of the deglitch circuit 700. In FIG. 7C, the CLK25 signal isprovided at the top and ten pulses are shown asserted on the DAV signal,where pulses 1 and 2 have durations greater than 6 but less than 12.5ns, pulses 3 and 4 have durations greater than 12.5 but less than 25 ns,pulses 5 and 6 have durations greater than 25 but less than 37.5 ns,pulses 7 and 8 have durations greater than 37.5 but less than 50 ns andwhere pulses 9 and 10 have durations greater than 50 ns. For purposes ofillustration, pulses 3, 5, 7 and 10 have slightly longer durations thancorresponding respective pulses 4, 6, 8 and 9. The output of the mux 738is shown based on the DG0 and DG1 signals. In FIG. 7D, the CLK25 and DAVsignals are repeated and the SDAV signal is shown based on the DG0 andDG1 signals for cases 11, 10 and 00, respectively.

Inspection of FIG. 7D reveals that pulses 1 and 2, being less than 12.5ns, are not detected and thus are rejected in all three cases of theDG1, 0 signals. Pulses 3 and 4 are between 12.5 and 25 ns, yet onlypulse 3 is detected for the DG1, 0=00 case since pulse 3 encompasses twoconsecutive transitions of the CLK25 signal while pulse 4 does not. Bothpulses 3 and 4 are rejected by the DG 1, 0=10 and 11 cases. Pulses 5 and6 are both between 25 and 37.5 ns and thus are detected for the DG 1,0=00 case and yet rejected for the DG1, 0=11 case. Since pulse 5encompasses three consecutive CLK25 transitions while pulse 6 does not,pulse 5 is accepted and pulse 6 is rejected for the DG1, 0=10 case.Pulses 7 and 8 are both between 37.5 and 50 ns and thus are detected byboth DG1, 0=00, 10 cases, yet rejected by the DG1, 0=11 case. Finally,pulses 9 and 10 are between 50 and 75 ns and detected by both DG1, 0=00,10 cases, but only pulse 10 is detected by the DG1, 0=11 case since itencompasses three consecutive CLK25 rising edges, while pulse 9 doesnot. Although not shown, any pulses greater than 75 ns are detected byall three cases.

Referring now to FIG. 8, a schematic diagram of the time-stamp timer 408is shown. The time-stamp timer 408 includes a 16-bit counter circuit800, preferably including a 16-bit up-counter, which receives the CLK50clock signal at a clock input. The counter circuit 800 receives a signalN₋₋ CAP, which is asserted when any capture conditions are true exceptrollover of the counter circuit 800. The counter circuit 800 includes aninverted reset input receiving a signal TIMER₋₋ RST*, which is assertedby a three-input AND gate 804. An asterisk (*) at the end of a signalname denotes negative logic, where the signal is considered assertedwhen low and negated when high. Thus, the counter circuit 800 is clearedwhen TIMER₋₋ RST* is asserted low, so that the counter circuit 800 goesto zero and begins counting up again when TIMER₋₋ RST* is negated.

A D-type flip-flop 802 has its D input pulled high to logic one andreceives a CAP signal at its clock input. The CAP signal, describedfurther below, is asserted when any of several capture conditions aretrue including rollover of the timer 800. The flip-flop 802 asserts asignal STRT₋₋ TIM to one input of the AND gate 804 for starting thecounter circuit 800 if enabled and not in a reset state. The CAP₋₋ ENsignal is provided to the inverted reset input of the flip-flop 802 forkeeping the counter circuit 800 in the reset state if the CAP₋₋ ENsignal is deasserted when capture is not enabled. The AND gate 804receives the TS₋₋ EN signal, which is asserted to enable time-stamping.The AND gate 804 also receives a signal RST₋₋ TIM*, which is assertedlow to reset the counter circuit 800, as will be described more fullybelow. In this manner, the counter circuit 800 remains in a reset stateany time capturing or the time-stamp functions are disabled, or any timethe RST₋₋ TIM* signal is asserted, indicating the desire to reset thecounter circuit 800. Otherwise, the counter circuit 800 counts up from0, providing a 16-bit time value at its outputs as the signals T[15:0].The time signals T[15:0] are preferably separated into two 8-bitportions, where the T[15:8] signals are referred to as the TIM₋₋ HI byteand the T[7:0] signals are referred to as the TIM₋₋ LO byte (FIG. 13).

The counter circuit 800 asserts a time-out signal TO indicatingrollover. The TO signal could be asserted when the counter circuit 800reaches its maximum value of FFFFh, where the T[15:0] signals are all1's. In the preferred embodiment, however, the counter circuit 800counts up to the value FFFDh and asserts the TO signal at FFFDh, whichoccurs two CLK50 cycles before it reaches its maximum value of FFFFh.Upon the next CLK50 cycle, the counter circuit goes to FFFEh and negatesthe TO signal and two flip-flops 1106 and 1108 (FIG. 11) are clocked toassert the corresponding signals N₋₋ CAP and CAP. If the N₋₋ CAP signalis asserted when the counter circuit 800 reaches FFFEh indicating anormal capture condition has occurred, it stops counting at FFFEh sothat the value FFFEh is written into the FIFO 300 as a normal time-stampvalue. This distinguishes a normal capture from a rollover conditionoccurring without a capture. However, if the N₋₋ CAP signal is notasserted at FFFEh, the counter circuit 800 provides the maximum valueFFFFh at its output, which is then written to the FIFO 300 indicating arollover condition rather than a normal time-stamp value.

Time-stamping preferably does not start until the first capture aftertime-stamping has been enabled. The RST₋₋ TIM* signal ensures thecounter circuit 800 is held in the reset state until after the firstcapture and is reset upon each capture. Thus, the time-stamp for thefirst capture is preferably zero. Since the counter circuit 800 is resetafter each capture, each time-stamp value represents the elapsed timesince the previous capture. However, if a capture or trigger conditionis not met, the counter circuit 800 reaches its maximum value of FFFFhin approximately 3.28 ms. In the preferred embodiment, if the currenttime-stamp is referred to as x, and the number of time-outs or rolloverssince the last capture value is y, then the real time value RT in ns iscalculated by the following equation (1):

    RT(ns)=50(x+1)+3,276,750(y)                                (1)

Referring now to FIG. 9, a logic diagram is shown for identify captureconditions according to parallel poll responses on the GPIB 108. TheEOI(1) and ATN(1) signals are each provided to the inputs of a two-inputAND gate 900. The EOI(2) and ATN(2) signals are each provided to theinputs of another two-input AND gate 902. The outputs of the AND gates900, 902 are provided to the respective inputs of a two-input XOR gate904. The output of the AND gate 900 is also provided to the active lowreset inputs of a timer 906 and a D-type flip-flop 908. The timer 906 ispreferably a 2 microsecond (μs) timer including a simple up-counterclocked by the CLK50 signal. Thus, after 2 μs, the timer 906 provides atime-out signal, POLL₋₋ TO, which is asserted when 2 μs has elapsedsince the reset input of the timer 906 was deasserted. The POLL₋₋ TOsignal is provided to the D input of the flip-flop 908, having its clockinput receiving the CLK50 signal. The Q output of the flip-flop 908provides a signal POLL₋₋ TO, which is provided to the inverting input ofa two-input AND gate 910. The other, non-inverting input of the AND gate910 receives the POLL₋₋ TO signal. The output of the AND gate 910 isprovided to one input of a two-input OR gate 912, which receives theoutput of the XOR gate 904 at its other input. The output of the OR gate912 provides the CAP₋₋ IDY signal, which indicates appropriate captureconditions according to parallel responses on the GPIB 108.

Operation of the parallel poll circuitry of FIG. 9 is now described.When a parallel poll command is issued, the EOI and ATN signals are bothasserted. After a rising edge of the CLK50 signal, both EOI(1) andATN(1) are asserted thereby removing the reset condition to the timer906 and the flip-flop 908. Also, since the command was not issued in theprior CLK50 cycle, the EOI(2) and ATN(2) signals are not both assertedso that the XOR gate 904 and the OR gate 912 both assert their outputshigh, thereby asserting the CAP₋₋ IDY signal. As will be described morefully below, assertion of the CAP₋₋ IDY signal causes a sample of theGPIB 108 to be captured. Upon the next CLK50 cycle, the XOR gate 904deasserts its output low so that the OR gate 912 deasserts the CAP₋₋ IDYsignal. The XOR gate 904 keeps its output low until the parallel pollcommand is deasserted.

After 2 μs, the timer 906 asserts the POLL₋₋ TO signal while the QPOLL₋₋TO signal is still negated, so that the AND gate 910 asserts its outputcausing the OR gate 912 to assert the CAP₋₋ IDY signal once again. Thus,another sample of the GPIB 108 signals are captured after the GPIBdevices 110 have had 2 μs to respond. The flip-flop 908 is then clockedby CLK50 so that the QPOLL₋₋ TO signal is asserted, so that the OR gate912 deasserts the CAP₋₋ IDY signal. The QPOLL₋₋ TO signal remainsasserted until parallel poll command is deasserted. As described furtherbelow, sampled data is captured when the QPOLL₋₋ TO signal is assertedand while the CAP₋₋ DAT signal is asserted, where the assertion of CAP₋₋DAT indicates a change of any one of the DIO signals as describedpreviously. Thus, while the parallel poll command remains asserted, anyupdated responses by the GPIB devices 110 are captured. Finally, whenthe parallel poll command is deasserted, the XOR gate 904 once againasserts its output causing the OR gate to assert the CAP₋₋ IDY signal,causing one last capture of the DIO data signals at the end of theparallel poll command.

It is appreciated that at least three captures occur during a parallelpoll command, a first upon assertion of the command, a second captureafter 2 μs, and a third when the parallel poll command is deasserted.Further, more samples are captured anytime the DIO signals change stateindicating an updated response to the parallel poll command. Thus, aGPIB system according to the present invention captures all possibleresponses and updated responses to the parallel poll command.

Referring now to FIG. 10A, a logic diagram is shown for identifyingcertain predetermined capture conditions of the GPIB 108. The CAP₋₋ IFC,CAP₋₋ REN, CAP₋₋ ATN and CAP₋₋ SRQ signals are each provided to the fourinputs of a four-input OR gate 1000. The output of OR gate 1000 isprovided to one input of a two-input AND gate 1002, which receives acapture control line transition signal CP₋₋ CTL at its other input. TheCP₋₋ CTL signal is set in a capture setting register (CPSR) for enablingdetection of any changes of the IFC, REN, ATN and SRQ signals. The CAP₋₋DAC and CAP₋₋ RFD signals are provided to two inputs of a three-input ORgate 1004, which receives the CAP₋₋ DAV₋₋ UNASRT signal at its thirdinput. The output of the OR gate 1004 is provided to one input of atwo-input AND gate 1006, which receives a capture handshake linetransition enable signal CP₋₋ HS at its other input, which is set in theCPSR register.

The CAP₋₋ IDY signal is provided to one input of a two-input AND gate1008, which receives a capture on parallel poll response enable signalCP₋₋ PPR, which is set in the CPSR register. Thus, if the CP₋₋ PPR bitis set in the CPSR register, assertion of the CAP₋₋ IDY signal causes acapture of GPIB samples.

The CP₋₋ PPR and QPOLL₋₋ TO signals are provided to the respectiveinputs of a two-input AND gate 1010, providing its output to one inputof a two-input OR gate 1012, which receives a capture data enable signalCP₋₋ DAT at its other input. The CP₋₋ DAT bit is set in the CPSRregister. The output of the OR gate 1012 is provided to one input of atwo-input AND gate 1014, which receives the CAP₋₋ DAT signal at itsother input. Thus, if the CP₋₋ PPR bit is set and the QPOLL₋₋ TO signalis asserted, or if the CP₋₋ DAT bit is set, the GPIB signals arecaptured whenever the CAP₋₋ DAT signal is asserted.

Certain trigger capture conditions are indicated by signals CAP₋₋ STRIG,CP₋₋ TRIG, TMRK₋₋ EN and CAP₋₋ FRST₋₋ TRIG, where these signals will notbe further described. The CP₋₋ TRIG signal is provided to one input of atwo-input OR gate 1016 receiving the TMRK₋₋ EN signal at its otherinput. The output of the OR gate 1016 is provided to one input of atwo-input AND gate 1017, receiving the CAP₋₋ STRIG at its other input.The output of the AND gates 1002, 1006, 1008, 1014 and 1017 as well asthe CAP₋₋ FRST₋₋ TRIG signal are all provided to the respective inputsof a six-input OR gate 1018, which asserts a signal G₋₋ CAP when any ofthe capture conditions of the AND/OR logic described above is detectedand enabled.

FIG. 10B is a logic diagram for identifying certain capture conditionsfor capturing the DIO data and EOI signals. A signal CAP₋₋ DAV₋₋ ASSRT,developed by logic described in FIG. 7A and generally representingassertions of the DAV signal, is provided to one input of a two-inputAND gate 1020 having its other inverted input receiving the CAP₋₋ATN(2). The output of the AND gate 1020 provides a signal CAP₋₋ DABrepresenting a data byte transfer on the GPIB 108. The CAP₋₋ DAV₋₋ ASSRTand CAP₋₋ ATN(2) signals are also provided to both non-inverting inputsof a two-input AND gate 1022, which asserts a signal CAP₋₋ COMrepresenting a command transfer on the GPIB 108.

The CAP₋₋ DAV₋₋ ASSRT signal and a capture handshake line transitionsignal CP₋₋ HS are provided to the two inputs of two-input AND gate 1026which provides its output to one input of a three-input OR gate 1034.The CAP₋₋ COM and a capture command enable signal CP₋₋ COM are providedto the two inputs of a two-input AND gate 1028, which provides itsoutput to a second input of the OR gate 1034. The CAP₋₋ DAB signal isprovided to one input of a two-input AND gate 1030, which receives acapture data byte enable signal. CP₋₋ DAB at its other input. The outputof the AND gate 1030 is provided to the third input of the OR gate 1034.The CP₋₋ COM, CP₋₋ DAB and CP₋₋ HS enable signals are preferably set inthe CPSR register for enabling these particular capture conditions. Theoutput of the OR gate 1034 asserts a signal D₋₋ CAP, which is assertedwhen any of the enabled capture conditions detected by the AND gate1026, 1028, 1030 and 1032 are asserted.

Referring now to FIG. 11, a schematic diagram is shown of a circuit fordetecting any of the capture conditions. The G₋₋ CAP, D₋₋ CAP and FRC₋₋CAP signals are provided to the three inputs of a three-input OR gate1100. The output of OR gate 1100 is provided to one input of a two-inputOR gate 1102 and also to the D input of a D-type flip-flop 1106. The TOsignal from the counter circuit 800 is provided to the other input ofthe OR gate 1102, which has its output provided to the D input ofanother D-type flip-flop 1108. The CLK50 signal is provided to the clockinputs of both flip-flops 1106, 1108. The CAP₋₋ EN signal is provided toan inverting input of a two-input OR gate 1104 and a signal RESET isprovided to the other non-inverting input of the OR gate 1104. The RESETsignal is asserted upon any reset conditions of the GPIBanalyzer/controller card 106. The output of the OR gate 1104 is providedto the clear inputs of both flip-flops 1106, 1108. The Q output of theflip-flop 1106 provides the normal capture signal N₋₋ CAP, which isasserted when capturing is enabled and any time the predetermined orprogrammed capture conditions occur, as indicated by the G₋₋ CAP, D₋₋CAP and FRC₋₋ CAP signals. The Q output of the flip-flop 1108 assertsthe CAP signal, which is asserted upon the same capture conditions asfor the normal N₋₋ CAP signal, and also any time time-out of the countercircuit 800 occurs as indicated by the TO signal.

Referring now to FIG. 12A, a block diagram is shown of a capture statemachine 1200 for detecting and asserting capture conditions. The capturestate machine 1200 receives the RESET, CAP and TS₋₋ EN signals atrespective inputs, and also receives the CLK25 clock signal at its clockinput. The capture state machine 1200 provides two signals DAT, FWEN andthe RST₋₋ TIM* signal at its three outputs. As will be described morefully below, the DAT signal is asserted by the capture state machine1200 any time it is desired to capture sampled signals of the GPIB 108.The FWEN signal is a FIFO write enable signal provided to the FIFO 300when the sampled value is to be written into the FIFO 300. As describedpreviously, the capture state machine 1200 asserts the RST₋₋ TIM* signallow to reset the counter circuit 800.

FIG. 12B is a state machine diagram illustrating operation of thecapture state machine 1200. A first state 1202 is entered upon resetconditions when the RESET signal is asserted by the GPIBcontroller/analyzer card 106. In state 1202, the DAT signal is assertedand the FWEN and RST₋₋ TIM* signals are negated, where negation isindicated by a bar above the signal name in the Figures. Upon assertionof the CAP signal, indicating any of the data or control captureconditions described previously, the state machine 1200 enters a state1204 upon the next assertion of the CLK25 clock signal. The FWEN signalis asserted in state 1204 and the DAT signal is negated. The RST₋₋ TIM*signal remains negated. If the time-stamp function is disabled, asindicated by a TS₋₋ EN signal being negated, then the state machine 1200reenters state 1202 upon the next assertion of the CLK25 signal. If TS₋₋EN is asserted, the state machine 1200 enters state 1206 upon the nextassertion of the CLK25 signal. In state 1206, the FWEN, RST₋₋ TIM* andDAT signals are all asserted. Upon the next assertion of the CLK25signal, if CAP is asserted, the state machine 1200 reenters state 1204to write another group of data into the FIFO 302. Otherwise, the statemachine 1200 reenters state 1202 upon the next assertion of the CLK25clock signal.

In this manner, sampled signals from the GPIB 108 that meet the captureconditions are written into the FIFO 300 as indicated by the CAP signalbeing asserted. If time-stamping is enabled, the capture state machine1200 inserts a time-stamp value from the counter circuit 800 into thenext location of the FIFO 300 following the capture value, and thecounter circuit 800 is reset. If another capture condition is met beforethe next rising edge of the CLK25 signal, another sampled value iswritten into the FIFO 300 followed by another time-stamp value. It isnoted that since sampling primarily occurs at 50 ns intervals and thusat a 20 MHz rate, that insertion of the time-stamp value is easilyachieved since the capture state machine 1200 is clocked by the CLK25signal at a 40 MHz rate. Also, the DIO signals sampled asynchronouslywith assertion of the DAV signal are captured "synchronously" with thecapture state machine 1200 followed by a time-stamp value. It is notedthat the asynchronous samples have higher priority and are selected oversynchronous samples if occurring in the same 50 ns period. Sincetime-out of the counter circuit 800 is also a "capture" condition, adummy GPIB sample is written into the FIFO 300 followed by the maximumtime-stamp value of FFFFh.

Referring now to FIG. 13, a schematic diagram is shown of select logic1300, which is preferably located within the capture logic block 410,for providing selected data to the FIFO 300. The GPIB₋₋ CTL(2) signals,where the SDAV2 signal as shown in FIG. 7A is considered one of theGPIB₋₋ CTL(2) signals, are provided to 7 of 16 bits of the binary 10input of a 3-input, 16-bit mux 1302. The remaining 9 bits of the binary10 input receive the EOI(2) and the DIO(2) signals. The 16 bits of thebinary 11 input of the mux 1302 receives the GPIB₋₋ CTL(2), the DAV₋₋EOI(2) and the DAV₋₋ DIO(2) signals. The TIME₋₋ HI and TIME₋₋ LO bytesare provided to the 16 bits of the binary 0x input of the mux 1302,where "x" indicates a binary 0 or 1 (don't care). The first select inputof the mux 1302 is the DAT signal and the second is the D₋₋ CAP signal.In this manner, the DAT signal selects between GPIB signals and thetime-stamp value, and the D₋₋ CAP signal selects between "synchronous"signals, or GPIB signals latched using the CLK50 signal, and"asynchronous" signals, or GPIB signals latched by the DAV signal. It isnoted that the asynchronous signals include the CAP₋₋ COM and CAP₋₋ DABcases as well as cases with assertions of the DAV signal, with referenceto FIG. 10B.

The 16 output bits of the mux 1302 are provided to the D inputs of a setof 16 D-type flip-flops 1304, receiving the CLK25 signal at their clockinputs. The Q outputs of the flip-flops 1304 are provided to 16 inputsof the FIFO 300. The FIFO 300 receives the FWEN signal at its enableinput. Thus, sampled data and control signals from the GPIB 108, ortime-stamp values from the counter circuit 800, are captured into theFIFO 300 when the FWEN signal is asserted.

The N₋₋ CAP, CAP and DAT signals are provided to a timer rollover markercircuit 1310, which also receives the CLK25 signal for purposes ofsynchronization. The marker circuit 1310 determines whether a capture isdue to rollover of the counter circuit 800 as opposed to a normalcapture condition by the state of the N₋₋ CAP and CAP signals. Inparticular, if the N₋₋ CAP signal is not asserted and the CAP signal isasserted, then a rollover condition has occurred. The marker circuit1310 also includes memory for determining if the prior capture was dueto rollover or a normal capture condition for identifying a firstrollover from subsequent consecutive rollovers. If a rollover occurs andthe previous capture was a regular capture, so that the rollover is thefirst rollover, the marker circuit asserts a signal MARK into theseventeenth bit (bit 16) of the FIFO 300 indicating a first time-out(rollover) value. The DAT signal is used to mark the time-stamp time-outvalue rather than the associated capture data. Only the first time-outvalue is marked so that any subsequent, consecutive maximum time-outvalues equal to FFFFh are not marked. The microprocessor 124 executes asoftware routine to retrieve data from the FIFO 300 on a regular basis.The computer 102 should retrieve at least two lines (32-bits) once every3.28 ms to prevent overflow of the FIFO 300. This is a very slow rate sothat the computer 102 is easily able to keep the FIFO 300 fromoverflowing. While the TS₋₋ EN signal is asserted so that time-stampingis enabled, every other line in the FIFO 300 is a time-stamp value. Thecomputer 102 easily calculates the elapsed time between successive datacaptures according to equation (1) provided previously. In oneembodiment, the computer 102 monitors the MARK bit (bit 16) andgenerates an interrupt when the mark bit is set. This informs thesoftware that the time-stamp value is the first maximum value (FFFFh)since the last actual captured data value. The software respondinglycounts remaining consecutive occurrences of the maximum value. Inanother embodiment, the software simply compares each time-stamp valuewith the maximum value to identify the first and any subsequentconsecutive time-out occurrences. The timer rollover marker circuit 1310and the extra bit of the FIFO 300 would not be necessary.

It is now appreciated that a GPIB system according to the presentinvention includes several novel features for accurately capturingsamples from a GPIB, without missing important data transition events.Furthermore, the GPIB analyzer inserts time-stamp values for accuratelydetermining elapsed time between captured data signals. Since time-outof the time-stamp timer causes a capture condition, the real elapsedtime between any two captured samples is readily calculated throughsoftware.

Although the system and method of a GPIB analyzer according to thepresent invention has been described in connection with the preferredembodiment, it is not intended to be limited to the specific form setforth herein, but on the contrary, it is intended to cover suchalternatives, modifications, and equivalents, as can be reasonablyincluded within the spirit and scope of the invention as defined by theappended claims.

I claim:
 1. A parallel poll detection system for capturing signals of aGPIB in response to a parallel poll command, comprising:command logicfor detecting the assertion and subsequent deassertion of a parallelpoll command and correspondingly causing the GPIB signals to be capturedboth upon assertion and deassertion of said parallel poll command; and atimer circuit coupled to said command logic for causing the GPIB signalsto be captured a predetermined time after said parallel poll command isasserted.
 2. The parallel poll detection system of claim 1, wherein theGPIB signals include an end or identify (EOI) signal and an attention(ATN) signal which are both asserted to indicate a parallel pollcommand, said command logic comprising:first sampling logic for samplingthe EOI and ATN signals of the GPIB; second sampling logic coupled tosaid first sampling logic for sampling said sampled EOI and ATN signals;a logic gate coupled to said first sampling logic for detecting saidparallel poll command being asserted; and compare logic coupled to saidsecond sampling logic and said logic gate for detecting said parallelpoll command being asserted and subsequently negated.
 3. The parallelpoll detection system of claim 2, wherein said first and second samplinglogic each comprise a set of latches.
 4. The parallel poll detectionsystem of claim 2, wherein said logic gate comprises an AND gate.
 5. Theparallel poll detection system of claim 2, wherein said logic gate holdssaid timer circuit in a reset state while said parallel poll command isdeasserted.
 6. The parallel poll detection system of claim 1, furthercomprising:transition detect logic for coupling to the GPIB and coupledto said command logic for causing the GPIB signals to be captured if anytransitions of the GPIB signals occur while said parallel poll commandis asserted.
 7. The parallel poll detection system of claim 6, whereinsaid transition detect logic comprises:first sampling logic for couplingto the GPIB for sampling GPIB data signals; second sampling logiccoupled to said first sampling logic for sampling said sampled GPIB datasignals; and compare logic coupled to said first and second samplinglogic for detecting any changes of said GPIB signals.
 8. The parallelpoll detection system of claim 7, wherein said first and second samplinglogic each comprise a set of latches.
 9. The parallel poll detectionsystem of claim 7, wherein said compare logic comprises:a set ofexclusive OR logic gates coupled to said first and second sampling logicfor asserting a plurality of signals indicating changes of respectiveGPIB data signals; and an OR logic gate having multiple inputs forreceiving said plurality of signals for asserting a transition signalindicative of any changes of said GPIB data signals.
 10. The parallelpoll detection system of claim 1, wherein said timer is a twomicrosecond timer.
 11. A GPIB system for capturing signals of a GPIB inresponse to a parallel poll command, comprising:capture logic forcapturing GPIB signals; command logic coupled to said capture logic fordetecting the assertion and subsequent deassertion of a parallel pollcommand and correspondingly causing said capture logic to capture theGPIB signals both upon assertion and deassertion of said parallel pollcommand; and a timer circuit coupled to said capture logic and saidcommand logic for causing said capture logic to capture the GPIB signalsa predetermined time after said parallel poll command is asserted. 12.The GPIB system of claim 11, wherein said capture logic comprises:abuffer for capturing GPIB samples; and sampling logic for coupling tothe GPIB and coupled to said buffer for sampling the GPIB signals at apredetermined rate and for enabling said buffer to receive said sampledGPIB samples.
 13. The GPIB system of claim 11, furthercomprising:transition detect logic for coupling to the GPIB and coupledto said command logic and said capture logic for causing said capturelogic to capture the GPIB signals if any transitions of the GPIB signalsoccur while said parallel poll command is asserted.
 14. A method ofcapturing GPIB data signals from a GPIB in response to a parallel pollcommand, comprising the steps of:detecting a parallel poll commandasserted and subsequently negated on the GPIB; capturing the GPIB datasignals in response to said parallel poll command being asserted;capturing the GPIB data signals a predetermined time after said parallelpoll command is asserted; and capturing the GPIB data signals inresponse to said parallel poll command being negated.
 15. The method ofclaim 14, further comprising the step of:detecting any changes of theGPIB data signals while said parallel poll command is asserted andcorrespondingly capturing the GPIB data signals.
 16. The method of claim14, further comprising the steps offcontinually sampling the GPIBsignals; and wherein each said capturing step comprises the step ofstoring the current samples of the GPIB data signals into a buffer. 17.The method of claim 14, wherein said step of detecting a parallel pollcommand comprises the step of detecting an end or identify (EOI) signaland an attention (ATN) signal on the GPIB asserted concurrently.
 18. Themethod of claim 14, wherein said step of capturing the GPIB data signalsa predetermined time after a parallel poll command is asserted comprisesthe steps of:initiating a timer upon detecting a parallel poll commandbeing asserted; and upon timeout of said timer, capturing the GPIB datasignals.
 19. The method of claim 14, wherein the predetermined time istwo microseconds.